Arrangement for runtime compensation of a runtime difference arising through emulation of a high frequency signal

ABSTRACT

An arrangement for runtime compensation of a runtime difference, arising through emulation of a high frequency signal, is disclosed, with a signal x(t), for emulation by a signal processing device, which emulates the signal x(t) with a signal x(t) and a device for determining a difference signal between the signals x(t) and x(t). The arrangement is characterized in that the emulated signal x(t) is conducted via filter with a negative group runtime for certain frequency ranges.

CROSS REFERENCE TO RELATED APPLICATIONS

[0001] This application is based on and hereby claims priority to PCT Application No. PCT/EP02/00656 filed on and Jan. 23, 2002 and German Application No. 101 03 812.7 filed on Jan. 29, 2001 and European Application No. 011 01 968.4 filed on Jan. 29, 2001, the contents of which are hereby incorporated by reference.

BACKGROUND OF THE INVENTION

[0002] The present invention relates to an arrangement for runtime compensation of a runtime difference arising through emulation of a high frequency signal.

[0003] High frequency signals, transmitted by any transmission systems of a linear or non-linear nature, such as amplifier chains for example, can be emulated by signal processing devices. One example of a transmission system is set out in the patent application filed by the applicant with the same application date, relating to a sigma-delta modulator for digitizing analog high frequency signals. Ideally the signal emulation of the output signal of the transmission system proceeds without a time delay in relation to the original signal, so that the precisely emulated signal components of the emulated signal extinguish the original signal completely in a difference signal.

[0004] Practical instances of signal emulation however generally result in a runtime difference between the emulated signal and the original signal. As can be clarified below, the time delay of the emulated signal results in extinction of the signal components in a certain frequency range only. Here x(t) designates the original output signal of the transmission system and {circumflex over (x)}(t) the emulated signal; τ stands for the runtime difference of the emulated signal.

[0005] The following equation applies

x(t)−{circumflex over (x)}(t)≈x(t)−x(t−τ)

X(jω)−_(e) ^(−jωτ) X(jω)=X(jω).(1−_(e) ^(−jωτ))

[0006] In order to achieve broadband signal extinction, runtime elements are commonly used, which delay the signal x(t) by the period of the runtime difference τ of signal emulation {circumflex over (x)}(t).

x(t−τ)−{circumflex over (x)}(t)≈x(t−τ)−x(t−τ)=0

[0007] The highly linear runtime elements used for this are technically expensive due to the high level of spectral purity of the signal x(t) and give rise to high manufacturing costs.

SUMMARY OF THE INVENTION

[0008] One possible object of the invention is therefore to create an arrangement for runtime compensation of a runtime difference arising through emulation of a high frequency signal, which allows broadband signal emulation and is simple to set up from a technical point of view.

[0009] This object may be achieved by an arrangement for runtime compensation of a runtime difference arising through emulation of a high frequency signal with a signal to be emulated x(t), with a signal processing device, which emulates the signal x(t) with a signal {circumflex over (x)}(t), and with a device for determining a difference signal between the signals x(t) and {circumflex over (x)}(t), which is characterized in that the emulated signal {circumflex over (x)}(t) is routed via a filter with a negative group runtime for certain frequency ranges. The parameters of the filter are selected so that the overall transmission function of the difference signal in the required frequency range has zeros or is significantly attenuated. This means that the runtime difference arising from signal emulation is compensated to the maximum degree possible in this frequency range.

[0010] According to one embodiment of the invention the signal x(t) forms the output signal of a transmission signal and a signal u(t) forms the input signal of the transmission system. The transmission system here can comprise an amplifier or even an amplifier chain. However any linear or non-linear transmission system can be used.

[0011] According to a further embodiment of the invention the arrangement has a regulation device, which can be used to modify the emulated signal {circumflex over (x)}(t), so that the difference signal is minimal.

[0012] The difference signal for regulating signal emulation is preferably routed to the signal processing device.

[0013] According to one embodiment of the invention a signal evaluation unit is provided, which evaluates the difference signal and routes the evaluated signal to the signal processing device.

[0014] According to a preferred embodiment of the invention, the analog input signal for controlling signal emulation is routed to the signal processing device.

[0015] The filter preferably has runtime elements, which delay the digital signal.

[0016] A linear filter is preferably used to achieve the object. An FIR, IIR or any other linear filter can for example be used.

BRIEF DESCRIPTION OF THE DRAWINGS

[0017] These and other objects and advantages of the present invention will become more apparent and more readily appreciated from the following description of the preferred embodiments, taken in conjunction with the accompanying drawings of which:

[0018]FIG. 1 is an illustration of a system for signal emulation according to the related art,

[0019]FIG. 2 is an illustration of a system, according to one aspect of the invention, for signal emulation,

[0020]FIG. 3 is an illustration of a further embodiment of a system according to the invention for signal emulation,

[0021]FIG. 4 is an illustration of an example of the application of the system according to the invention for signal emulation, and

[0022]FIG. 5 is an illustration of a second embodiment of a system according to the invention for signal emulation.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

[0023] Reference will now be made in detail to the preferred embodiments of the present invention, examples of which are illustrated in the accompanying drawings, wherein like reference numerals refer to like elements throughout

[0024] The arrangement shown in FIG. 1 for signal emulation, as known from the related art, has an input signal u(t), which is transmitted by any linear or non-linear transmission system 1. The signal x(t) is present at the output of the transmission system 1. The signal x(t) is emulated in the signal processing device 2 with runtime differences, i.e. delays, arising in relation to the signal x(t). The signal {circumflex over (x)}(t) is present at the output of the signal processing device 2. A runtime element 3 is provided for the signal x(t) to compensate for runtime differences and this delays the signal x(t) for a time τ. Here τ is preferably selected so that it corresponds to the runtime difference produced by the signal processing device 2. Assuming ideal signal emulation and a delay τ, which corresponds precisely to the signal delay produced by signal emulation, the following applies for the difference signal x(t−τ)−{circumflex over (x)}(t) created from {circumflex over (x)}(t) and the delayed signal x(t−τ) for all frequencies

x(t−τ)−{circumflex over (x)}(t)=0

[0025] A control loop can be created to improve signal emulation and this transmits the difference signal, which is usually not equal to 0, to the signal processing device 2. The delayed signal x(t−τ) can also be used as a control variable.

[0026] With the system there may be no need to use a runtime element to compensate for the runtime difference. An illustration of the system is shown in FIG. 2.

[0027] The emulated signal {circumflex over (x)}(t) is passed as the input signal to a linear filter 4. An FIR, IIR or any other linear filter can be used here. The coefficients of the linear filter are selected so that for certain frequency ranges the runtime difference produced by the signal processing device 2 is compensated for by the linear filter. In certain frequency ranges the filter used has a negative group runtime but is still causal and therefore feasible because of positive group runtimes in other frequency ranges, i.e. signal delays. In this way signal emulation is achieved in the required frequency range, which is a broader band compared with previous solutions and is simple to set up because of the digital filters used. The difference signal formed at the summing unit 5 can be used as a control variable for the signal processing device 2. It is however conceivable for an evaluation result of the difference signal to be used as the control variable. A signal evaluation unit 6 is used for this and converts the difference signal into a Taylor series for example. Other types of signal breakdown can also be used.

[0028] A further example of signal breakdown is the spectral analysis (Fourier analysis) of the difference signal. The object is to minimize the power of the difference signal within a sub-band. For this it is sufficient to send to the signal processing device 2 those results of the spectral analysis of the difference signal, which describe the frequency response within the relevant sub-band.

[0029] The power of the error signal (difference signal) within the relevant frequency band can be used as a further alternative parametric control variable.

[0030] An embodiment of the invention is described below using an example according to FIG. 3. In this example an FIR filter 4 a is used to achieve negative group runtime for certain frequency ranges. Runtime compensation is to be carried out in the low-pass range. The following is to apply for the delay elements τ′ of the filter

τ′=τ,

[0031] i.e. the delay elements t′ of the filter each correspond to the runtime difference t of the signal processing device. The starting point is established by a linear filter design with good attenuation at the frequency ω=0: $H_{Design} = {1 - {\sum\limits_{l = 1}^{q - 1}\quad {a_{l}z^{- l}}}}$

[0032] where q=1, 2, 3, . . . and 1=1, 2, 3, . . . .

[0033] In this example

H _(Design)=(1−_(z) ⁻¹)^(ν)

[0034] is selected with ν=2 and z=e^(jωτ). The following therefore results at the output of the summing unit 5 for the difference signal y(t) ${y(t)} = {{{x(t)} + {\sum\limits_{l = 1}^{q - 1}\quad {a_{l}{\hat{x}\left( {t - {\left( {l - 1} \right)\tau}} \right)}}}} = {{{x(t)} - {2{\hat{x}(t)}} + {\hat{x}\left( {t - \tau} \right)}} \approx {{x(t)} - {2{x\left( {t - \tau} \right)}} + {x\left( {t - {2\tau}} \right)}}}}$

[0035] The following follows from the linearity of the Fourier transformation

Y(e ^(jω))=(1−e ^(jωτ))² X(e ^(jω))=(1−2e ^(−jωτ) +e ^(−jω2τ))X(^(jω))=X(e ^(jω))−2e ^(−jωτ) X(e ^(jω))+e ^(−jω2τ) X(e ^(jω))

[0036] corresponds to

y(t)=x(t)−2x(t−τ)+x(t+2τ)

[0037] The definition of group runtime according to K. D. Kammeyer, Nachrichtenübertragung (Message Transmission), Teubner Stuttgart 1996, is as follows ${\tau_{g}(\omega)} = {- \frac{{\varphi (\omega)}}{\omega}}$

[0038] Frequency response of the relevant sub-system

H _(Sub)=2−e ^(jωτ)

[0039] At frequencies ωτ≈2π, _(e) ^(−jω2π)≈1−j(ωτ−2π) (Taylor series development). The following then applies approximately

H _(Sub)=2−(1−j(ωτ−2π))=1+j(ωτ−2π))

[0040] The phase is approximately ωτ−2π, the differential derivation to ω results in negative values: −τ is the group runtime to be compensated.

[0041] Therefore the coefficients α₁ . . . α_(n) are selected as follows for the filter shown: α₁=2, α₂=−1 and α₃ . . . α_(n)=0.

[0042] A specific example of the application of the invention is shown in FIG. 4. A cascade stage of an analog-digital converter system with a low-pass sigma-delta modulator 7 is shown, which is the subject of a further patent application by the applicant. The digital signal emulation of the analog input signal u(t) is achieved here byf the low-pass sigma-delta modulator 7. The two output signals of a signal processing device 2 a, result from the multiplication of the input signal u(t) and a sin or cos signal and are designated as inphase or quadrature components, are combined again to form a signal in the digital mixer 8 and then converted to analog in a band-pass digital-analog converter 9. The output signal of the band-pass digital-analog converter 9 is routed with a negative sign to a summing unit 10. The input signal u(t) is amplified for amplitude adjustment in an amplifier 11 and reaches the summing unit 10. According to the related art the signal u(t) is also delayed in order to compensate for the delay to the input signal introduced by the signal processing device 2 a.

[0043] Achievement of runtime compensation based on the example of an application shown in FIG. 4 is shown in FIG. 5. A digital filter with the coefficients α₁=2 and α₂=−1 is used here. As disclosed above, this filter has a high level of attenuation at ω=0. The inphase and quadrature components of the low-pass sigma-delta modulator 7 are routed via a digital mixer 8, multiplied by the coefficient α₁=2 and converted to an analog signal in a band-pass digital-analog converter 9.

[0044] The signal with a negative sign is then routed to a summing unit 10. The inphase and quadrature components of the low-pass sigma-delta modulator 7 are delayed by τ in a delay element 12, combined in a mixer 8 a and multiplied by the coefficient α₂=−1. After conversion to an analog signal in a band-pass digital-analog converter 9 a, the signal is routed to the summing unit 10 with a negative sign. The input signal u(t) undergoes an amplitude adjustment by an amplifier 11 but is not delayed as in FIG. 4. The filter downstream from the digital mixer means that frequencies in the range ω=2π have a negative group runtime, so the delay produced by the signal processing device 2 a is compensated for this frequency range. In other frequency ranges the group runtime is positive but the output signal is still band-limited, so no additional restriction results due to the digital filter.

[0045] The invention has been described in detail with particular reference to preferred embodiments thereof and examples, but it will be understood that variations and modifications can be effected within the spirit and scope of the invention. 

1. Arrangement for runtime compensation of a runtime difference arising through emulation of a high frequency signal with a signal to be emulated x(t), with a signal processing device, which emulates the signal x(t) with a signal {circumflex over (x)}(t), and with a device for determining a difference signal between the signals x(t) and {circumflex over (x)}(t), characterized in that the emulated signal {circumflex over (x)}(t) is routed via a filter with negative group runtime for certain frequency ranges.
 2. Arrangement according to claim 1, characterized in that the signal x(t) forms the output signal of a transmission system and a signal u(t) forms the input signal of the transmission system.
 3. Arrangement according to claim 1 or 2, characterized in that it has a regulation device, by means of which the emulated signal {circumflex over (x)}(t), can be modified so that the difference signal becomes minimal.
 4. Arrangement according to claim 3, characterized in that the difference signal for regulating signal emulation is routed to the signal processing device.
 5. Arrangement according to one of the preceding claims, characterized in that a signal evaluation unit is provided, which evaluates the difference signal and routes the evaluated signal to the signal processing device. Arrangement according to one of the preceding claims, characterized in that the analog input signal for controlling signal emulation is routed to the signal processing device.
 6. Arrangement according to one of the preceding claims, characterized in that the filter has runtime elements.
 7. Arrangement according to one of the preceding claims, characterized in that the filter is linear.
 8. Arrangement according to one of claims 1 to 8, characterized in that the filter is an FIR filter.
 9. Arrangement according to one of claims 1 to 8, characterized in that the filter is an IIR filter. 